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650 kHz /1.3 MHz Step-Up PWM DC-to-DC Switching Converters ADP1612/ADP1613
FEATURES
Current limit 1.4 A for the ADP1612 2.0 A for the ADP 1613 Minimum input voltage 1.8 V for the ADP1612 2.5 V for the ADP1613 Pin-selectable 650 kHz or 1.3 MHz PWM frequency Adjustable output voltage up to 20 V Adjustable soft start Undervoltage lockout Thermal shutdown 8-lead MSOP
TYPICAL APPLICATION CIRCUIT
L1
VIN
6
ADP1612/ ADP1613
VIN EN FB 2
7
D1 SW 5 R1
VOUT
ON OFF CIN 650kHz (DEFAULT) 1.3MHz FREQ SS GND
4 3
R2 COMP 1 RCOMP CCOMP COUT
06772-001
8
CSS
Figure 1. Step-Up Regulator Configuration
APPLICATIONS
TFT LCD bias supplies Portable applications Industrial/instrumentation equipment
100 90 80 VIN = 5V fSW = 1.3MHz TA = 25C
GENERAL DESCRIPTION
The ADP1612/ADP1613 are step-up dc-to-dc switching converters with an integrated power switch capable of providing an output voltage as high as 20 V. With a package height of less than 1.1 mm, the ADP1612/ADP1613 are optimal for spaceconstrained applications such as portable devices or thin film transistor (TFT) liquid crystal displays (LCDs). The ADP1612/ADP1613 operate in current mode pulse-width modulation (PWM) with up to 94% efficiency. Adjustable soft start prevents inrush currents when the part is enabled. The pin-selectable switching frequency and PWM current-mode architecture allow for excellent transient response, easy noise filtering, and the use of small, cost-saving external inductors and capacitors. Other key features include undervoltage lockout (UVLO), thermal shutdown (TSD), and logic controlled enable. The ADP1612/ADP1613 are available in the lead-free 8-lead MSOP.
EFFICIENCY (%)
70
60 50 40 ADP1612, ADP1612, ADP1613, ADP1613, 1 10 100 LOAD CURRENT (mA) V OUT = 12V V OUT = 15V V OUT = 12V V OUT = 15V 1k
06772-009
30
Figure 2. ADP1612/ADP1613 Efficiency for Various Output Voltages
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.
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ADP1612/ADP1613 TABLE OF CONTENTS
Features .............................................................................................. 1 Applications ....................................................................................... 1 Typical Application Circuit ............................................................. 1 General Description ......................................................................... 1 Revision History ............................................................................... 2 Specifications..................................................................................... 3 Absolute Maximum Ratings............................................................ 4 Thermal Resistance ...................................................................... 4 Boundary Condition .................................................................... 4 ESD Caution .................................................................................. 4 Pin Configuration and Function Descriptions ............................. 5 Typical Performance Characteristics ............................................. 6 Theory of Operation ...................................................................... 11 Current-Mode PWM Operation .............................................. 11 Frequency Selection ................................................................... 11 Soft Start ...................................................................................... 11 Thermal Shutdown (TSD)......................................................... 12 UnderVoltage Lockout (UVLO) ............................................... 12 Enable/Shutdown Control ........................................................ 12 Applications Information .............................................................. 13 Setting the Output Voltage ........................................................ 13 Inductor Selection ...................................................................... 13 Choosing the Input and Output Capacitors ........................... 13 Diode Selection........................................................................... 14 Loop Compensation .................................................................. 14 Soft Start Capacitor .................................................................... 15 Typical Application Circuits ......................................................... 16 Step-Up Regulator ...................................................................... 16 Step-Up Regulator Circuit Examples ....................................... 16 SEPIC Converter ........................................................................ 22 TFT LCD Bias Supply ................................................................ 22 PCB Layout Guidelines .................................................................. 24 Outline Dimensions ....................................................................... 25 Ordering Guide .......................................................................... 25
REVISION HISTORY
9/09--Rev. 0 to Rev. A Changes to Figure 45 ...................................................................... 17 Changes to Figure 48 and Figure 51 ............................................. 18 Changes to Figure 54 and Figure 57 ............................................. 19 Changes to Figure 60 and Figure 63 ............................................. 20 Changes to Figure 66 and Figure 69 ............................................. 21 Changes to Figure 72 ...................................................................... 22 Changes to Ordering Guide .......................................................... 25 4/09--Revision 0: Initial Version
Rev. A | Page 2 of 28
ADP1612/ADP1613 SPECIFICATIONS
VIN = 3.6 V, unless otherwise noted. Minimum and maximum values are guaranteed for TJ = -40C to +125C. Typical values specified are at TJ = 25C. All limits at temperature extremes are guaranteed by correlation and characterization using standard statistical quality control (SQC), unless otherwise noted. Table 1.
Parameter SUPPLY Input Voltage Quiescent Current Nonswitching State Shutdown Switching State 1 Enable Pin Bias Current OUTPUT Output Voltage Load Regulation REFERENCE Feedback Voltage Line Regulation ERROR AMPLIFIER Transconductance Voltage Gain FB Pin Bias Current SWITCH SW On Resistance SW Leakage Current Peak Current Limit 2 OSCILLATOR Oscillator Frequency Maximum Duty Cycle FREQ Pin Current EN/FREQ LOGIC THRESHOLD Input Voltage Low Input Voltage High SOFT START SS Charging Current SS Voltage UNDERVOLTAGE LOCKOUT (UVLO) Undervoltage Lockout Threshold Symbol VIN Conditions ADP1612 ADP1613 VFB = 1.5 V, FREQ = VIN VFB = 1.5 V, FREQ = GND VEN = 0 V FREQ = VIN, no load FREQ = GND, no load VEN = 3.6 V VIN ILOAD = 10 mA to 150 mA, VIN = 3.3 V, VOUT = 12 V VFB ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V GMEA AV I = 4 A VFB = 1.3 V RDSON ICL ISW = 1.0 A VSW = 20 V ADP1612, duty cycle = 70% ADP1613, duty cycle = 70% FREQ = GND FREQ = VIN COMP = open, VFB = 1 V, FREQ = VIN FREQ = 3.6 V ADP1612, VIN = 1.8 V to 5.5 V; ADP1613, VIN = 2.5 V to 5.5 V 1.2041 0.1 1.235 0.07 80 60 1 130 0.01 1.4 2.0 650 1.3 90 5 1.2659 0.24 Min 1.8 2.5 900 700 0.01 4 2.2 3.3 Typ Max 5.5 5.5 1350 1300 2 5.8 4 7 20 Unit V V A A A mA mA A V mV/mA V %/V A/V dB nA m A A A kHz MHz % A V V A V V V V V C C
IQ IQSHDN IQSW IEN VOUT
50 300 10 1.9 2.5 720 1.4 8 0.3
0.9 1.3 500 1.1 88
fSW DMAX IFREQ VIL VIH ISS VSS
1.6 VSS = 0 V VFB = 1.3 V ADP1612, VIN rising ADP1612, VIN falling ADP1613, VIN rising ADP1613, VIN falling 3.4 5 1.2 1.70 1.62 2.25 2.16 150 20 6.2
THERMAL SHUTDOWN Thermal Shutdown Threshold Thermal Shutdown Hysteresis
1 2
This parameter specifies the average current while switching internally and with SW (Pin 5) floating. Current limit is a function of duty cycle. See the Typical Performance Characteristics section for typical values over operating ranges. Rev. A | Page 3 of 28
ADP1612/ADP1613 ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter VIN, EN, FB to GND FREQ to GND COMP to GND SS to GND SW to GND Operating Junction Temperature Range Storage Temperature Range Soldering Conditions ESD (Electrostatic Discharge) Human Body Model Rating -0.3 V to +6 V -0.3 V to VIN + 0.3 V 1.0 V to 1.6 V -0.3 V to +1.3 V 21 V -40C to +125C -65C to +150C JEDEC J-STD-020 5 kV
THERMAL RESISTANCE
Junction-to-ambient thermal resistance (JA) of the package is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. The junction-toambient thermal resistance is highly dependent on the application and board layout. In applications where high maximum power dissipation exists, attention to thermal board design is required. The value of JA may vary, depending on PCB material, layout, and environmental conditions. Table 3.
Package Type 8-Lead MSOP 2-Layer Board1 4-Layer Board1
1
JA 206.9 162.2
JC 44.22 44.22
Unit C/W C/W
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. Absolute maximum ratings apply individually only, not in combination.
Thermal numbers per JEDEC standard JESD 51-7.
BOUNDARY CONDITION
Modeled under natural convection cooling at 25C ambient temperature, JESD 51-7, and 1 W power input with 2- and 4-layer boards.
ESD CAUTION
Rev. A | Page 4 of 28
ADP1612/ADP1613 PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
COMP 1 FB 2 EN 3 GND 4
ADP1612/ ADP1613
TOP VIEW (Not to Scale)
8 7 6 5
SS FREQ
06772-002
VIN SW
Figure 3. Pin Configuration
Table 4. Pin Function Descriptions
Pin No. 1 2 3 4 5 6 7 8 Mnemonic COMP FB EN GND SW VIN FREQ SS Description Compensation Input. Connect a series resistor-capacitor network from COMP to GND to compensate the regulator. Output Voltage Feedback Input. Connect a resistive voltage divider from the output voltage to FB to set the regulator output voltage. Enable Input. Drive EN low to shut down the regulator; drive EN high to turn on the regulator. Ground. Switching Output. Connect the power inductor from the input voltage to SW and connect the external rectifier from SW to the output voltage to complete the step-up converter. Main Power Supply Input. VIN powers the ADP1612/ADP1613 internal circuitry. Connect VIN to the input source voltage. Bypass VIN to GND with a 10 F or greater capacitor as close to the ADP1612/ADP1613 as possible. Frequency Setting Input. FREQ controls the switching frequency. Connect FREQ to GND to program the oscillator to 650 kHz, or connect FREQ to VIN to program it to 1.3 MHz. If FREQ is left floating, the part defaults to 650 kHz. Soft Start Timing Capacitor Input. A capacitor connected from SS to GND brings up the output slowly at powerup and reduces inrush current.
Rev. A | Page 5 of 28
ADP1612/ADP1613 TYPICAL PERFORMANCE CHARACTERISTICS
VEN = VIN and TA = 25C, unless otherwise noted.
100 90 80 VIN = 3.3V fSW = 650kHz TA = 25C ADP1612 90 80 100 VIN = 5V fSW = 1.3MHz TA = 25C ADP1612
EFFICIENCY (%)
70
EFFICIENCY (%)
VOUT = 5V VOUT = 12V VOUT = 15V
06772-012
70
60 50 40
60 50 40
VOUT = 12V VOUT = 15V 1 10 100 LOAD CURRENT (mA) 1k
06772-028 06772-030 06772-029
30 1 10 100 LOAD CURRENT (mA) 1k
30
Figure 4. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 650 kHz
Figure 7. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
100 90 80 VIN = 3.3V fSW = 1.3MHz TA = 25C ADP1612
100 90 80 VIN = 5V fSW = 650kHz TA = 25C ADP1613
EFFICIENCY (%)
70
EFFICIENCY (%)
VOUT = 5V VOUT = 12V VOUT = 15V 1 10 100 LOAD CURRENT (mA) 1k
06772-026
70
60 50 40
60 50 40 VOUT = 12V VOUT = 15V VOUT = 20V 1 10 100 LOAD CURRENT (mA) 1k
30
30
Figure 5. ADP1612 Efficiency vs. Load Current, VIN = 3.3 V, fSW = 1.3 MHz
Figure 8. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
100 90 80 VIN = 5V fSW = 650kHz TA = 25C ADP1612
100 90 80 VIN = 5V fSW = 1.3MHz TA = 25C ADP1613
EFFICIENCY (%)
70
EFFICIENCY (%)
70
60 50 40
60 50 40 VOUT = 12V VOUT = 15V VOUT = 20V 1 10 100 LOAD CURRENT (mA) 1k
VOUT = 12V VOUT = 15V 1 10 100 LOAD CURRENT (mA) 1k
06772-027
30
30
Figure 6. ADP1612 Efficiency vs. Load Current, VIN = 5 V, fSW = 650 kHz
Figure 9. ADP1613 Efficiency vs. Load Current, VIN = 5 V, fSW = 1.3 MHz
Rev. A | Page 6 of 28
ADP1612/ADP1613
2.4 ADP1612 2.2
3.4 ADP1613 3.2 3.0 TA = +25C 2.8
CURRENT LIMIT (A)
2.0
TA = +25C
1.8
CURRENT LIMIT (A)
2.6 2.4 2.2 TA = +85C
1.6
TA = -40C
TA = -40C
1.4
TA = +85C
06772-010
2.3
2.8 3.3 3.8 INPUT VOLTAGE (V)
4.3
4.8
3.0
3.5 4.0 INPUT VOLTAGE (V)
4.5
Figure 10. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 5 V
Figure 13. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 5 V
2.0 ADP1612
2.6 ADP1613
1.8
2.4
TA = +25C
CURRENT LIMIT (A)
1.6
CURRENT LIMIT (A)
TA = +25C
2.2
1.4 TA = -40C 1.2 TA = +85C
2.0
TA = -40C TA = +85C
06772-013
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
3.0
3.5
4.0
4.5
5.0
5.5
INPUT VOLTAGE (V)
Figure 11. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 8 V
Figure 14. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 8 V
1.6 ADP1612
2.6 ADP1613 2.4
1.4
CURRENT LIMIT (A)
CURRENT LIMIT (A)
TA = -40C
TA = +25C
2.2
TA = -40C
1.2
2.0
1.0
TA = +85C
1.8 TA = +25C 1.6 TA = +85C
06772-011
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
3.0
3.5
4.0
4.5
5.0
5.5
INPUT VOLTAGE (V)
Figure 12. ADP1612 Switch Current Limit vs. Input Voltage, VOUT = 15 V
Figure 15. ADP1613 Switch Current Limit vs. Input Voltage, VOUT = 15 V
Rev. A | Page 7 of 28
06772-033
0.8 1.8
1.4 2.5
06772-032
1.0 1.8
1.8 2.5
06772-031
1.2 1.8
2.0 2.5
ADP1612/ADP1613
800 ADP1612/ADP1613 750 5 700 650 600 550 500 450
06772-014 06772-018
6 ADP1612/ADP1613 TA = +25C
TA = +125C
QUIESCENT CURRENT (mA)
QUIESCENT CURRENT (A)
4
TA = +125C TA = -40C
TA = -40C TA = +25C
3
2
400 1.8
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
1 1.8
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
Figure 16. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Nonswitching, fSW = 650 kHz
800 ADP1612/ADP1613
Figure 19. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Switching, fSW = 1.3 MHz
250 ISW = 1A 230 ADP1612/ADP1613
750
QUIESCENT CURRENT (A)
210 700 TA = +125C 190 TA = +30C TA = +85C
RDSON (m)
TA = -40C TA = +25C
170 150 130 110 90 TA = -40C
650
600
550
06772-017
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
Figure 17. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Nonswitching, fSW = 1.3 MHz
3.5 ADP1612/ADP1613
Figure 20. ADP1612/ADP1613 On Resistance vs. Input Voltage
250 ADP1612/ADP1613 230 VIN = 1.8V TA = +25C 210 190 ISW = 1A
3.0
QUIESCENT CURRENT (mA)
RDSON (m)
2.5 TA = +125C 2.0 TA = -40C
170 150 130
VIN = 2.5V
1.5
110 VIN = 3.6V 90 VIN = 5.5V
06772-015 06772-019
1.0 1.8
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
70 -40
-15
10 35 TEMPERATURE (C)
60
85
Figure 18. ADP1612/ADP1613 Quiescent Current vs. Input Voltage, Switching, fSW = 650 kHz
Figure 21. ADP1612/ADP1613 On Resistance vs. Temperature
Rev. A | Page 8 of 28
06772-016
500 1.8
70 1.8
ADP1612/ADP1613
660 ADP1612/ADP1613 650 TA = +25C 640
SS PIN CURRENT (A)
5.0 VIN = 1.8V 5.1 ADP1612/ADP1613
FREQUENCY (kHz)
4.9 VIN = 5.5V 4.8 VIN = 3.6V 4.7
630 620 TA = +125C 610 600
4.6
590 580 1.8
TA = -40C
06772-020
06772-024 06772-025
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
4.5 -40
-10
20 50 TEMPERATURE (C)
80
110
Figure 22. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 650 kHz
Figure 25. ADP1612/ADP1613 SS Pin Current vs. Temperature
1.32 ADP1612/ADP1613 1.30 1.28 TA = +25C
92.8 ADP1612/ADP1613 92.6 TA = +25C
MAXIMUM DUTY CYCLE (%)
92.4 92.2 92.0 91.8 91.6 91.4
TA = +125C
FREQUENCY (MHz)
1.26 1.24 1.22 1.20 1.18 1.16
06772-023
TA = -40C
TA = -40C
TA = +125C
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
Figure 23. ADP1612/ADP1613 Frequency vs. Input Voltage, fSW = 1.3 MHz
Figure 26. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage, fSW = 650 kHz
93.4
7 ADP1612/ADP1613 6 TA = +125C
MAXIMUM DUTY CYCLE (%)
ADP1612/ADP1613 93.2 93.0 92.8 92.6
TA = +125C
TA = +25C
EN PIN CURRENT (A)
5 4
TA = -40C 92.4 92.2 92.0 91.8
3 2 1
TA = +25C
TA = -40C
06772-021
0 0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 EN PIN VOLTAGE (V) 4.0 4.5 5.0 5.5
91.6 1.8
2.3
2.8
3.3 3.8 4.3 INPUT VOLTAGE (V)
4.8
5.3
Figure 24. ADP1612/ADP1613 EN Pin Current vs. EN Pin Voltage
Figure 27. ADP1612/ADP1613 Maximum Duty Cycle vs. Input Voltage, fSW = 1.3 MHz
Rev. A | Page 9 of 28
06772-022
1.14 1.8
91.2 1.8
ADP1612/ADP1613
T OUTPUT VOLTAGE (5V/DIV) VIN = 5V VOUT = 12V ILOAD = 20mA L = 6.8H fSW = 1.3MHz COUT = 10F
T OUTPUT VOLTAGE (5V/DIV) VIN = 5V VOUT = 12V ILOAD = 250mA L = 6.8H fSW = 1.3MHz
SWITCH VOLTAGE (10V/DIV)
INDUCTOR CURRENT (200mA/DIV)
INDUCTOR CURRENT (2A/DIV)
SWITCH VOLTAGE (10V/DIV)
EN PIN VOLTAGE (5V/DIV)
06772-034 06772-037 06772-039 06772-038
TIME (400ns/DIV)
TIME (20ms/DIV)
Figure 28. ADP1612/ADP1613 Switching Waveform in Discontinuous Conduction Mode
Figure 31. ADP1612/ADP1613 Start-Up from VIN, CSS =100 nF
T OUTPUT VOLTAGE (5V/DIV) VIN = 5V VOUT = 12V ILOAD = 200mA L = 6.8H fSW = 1.3MHz COUT = 10F
T
OUTPUT VOLTAGE (5V/DIV)
SWITCH VOLTAGE (10V/DIV) VIN = 5V VOUT = 12V ILOAD = 250mA L = 6.8H fSW = 1.3MHz INDUCTOR CURRENT (500mA/DIV)
06772-035
INDUCTOR CURRENT (500mA/DIV)
SWITCH VOLTAGE (10V/DIV)
EN PIN VOLTAGE (5V/DIV) TIME (400s/DIV)
TIME (400ns/DIV)
Figure 29. ADP1612/ADP1613 Switching Waveform in Continuous Conduction Mode
Figure 32. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 33 nF
T VIN = 5V VOUT = 12V ILOAD = 250mA L = 6.8H fSW = 1.3MHz
T OUTPUT VOLTAGE (5V/DIV)
OUTPUT VOLTAGE (5V/DIV)
SWITCH VOLTAGE (10V/DIV) VIN = 5V VOUT = 12V ILOAD = 250mA L = 6.8H fSW = 1.3MHz INDUCTOR CURRENT (500mA/DIV)
06772-036
SWITCH VOLTAGE (10V/DIV)
INDUCTOR CURRENT (2A/DIV) EN PIN VOLTAGE (5V/DIV) TIME (20ms/DIV)
EN PIN VOLTAGE (5V/DIV) TIME (400s/DIV)
Figure 30. ADP1612/ADP1613 Start-Up from VIN, CSS =33 nF
Figure 33. ADP1612/ADP1613 Start-Up from Shutdown, CSS = 100 nF
Rev. A | Page 10 of 28
ADP1612/ADP1613 THEORY OF OPERATION
VIN CIN VIN
6
L1 >1.6V <0.3V
7
FREQ SW D1 VOUT COUT CURRENT SENSING
VIN
+ D COMPARATOR PWM COMPARATOR +
A
5
VOUT R1 R2 FB
2
ERROR AMPLIFIER
DREF
OSCILLATOR
VBG COMP VIN UVLOREF VSS 5A SS
8
5A UVLO COMPARATOR S Q R TSD COMPARATOR TSENSE TREF RESET BG BAND GAP N1 DRIVER
1
RCOMP CCOMP
SOFT START
CSS AGND 1.1M AGND
06772-003
ADP1612/AD1613
4
EN <0.3V
3
>1.6V
GND
Figure 34. Block Diagram with Step-Up Regulator Application Circuit
The ADP1612/ADP1613 current-mode step-up switching converters boost a 1.8 V to 5.5 V input voltage to an output voltage as high as 20 V. The internal switch allows a high output current, and the high 650 kHz/1.3 MHz switching frequency allows for the use of tiny external components. The switch current is monitored on a pulse-by-pulse basis to limit it to 1.4 A typical (ADP1612) or 2.0 A typical (ADP1613).
FREQUENCY SELECTION
The frequency of the ADP1612/ADP1613 is pin-selectable to operate at either 650 kHz to optimize the regulator for high efficiency or at 1.3 MHz for use with small external components. If FREQ is left floating, the part defaults to 650 kHz. Connect FREQ to GND for 650 kHz operation or connect FREQ to VIN for 1.3 MHz operation. When connected to VIN for 1.3 MHz operation, an additional 5 A, typical, of quiescent current is active. This current is turned off when the part is shutdown.
CURRENT-MODE PWM OPERATION
The ADP1612/ADP1613 utilize a current-mode PWM control scheme to regulate the output voltage over all load conditions. The output voltage is monitored at FB through a resistive voltage divider. The voltage at FB is compared to the internal 1.235 V reference by the internal transconductance error amplifier to create an error voltage at COMP. The switch current is internally measured and added to the stabilizing ramp. The resulting sum is compared to the error voltage at COMP to control the PWM modulator. This current-mode regulation system allows fast transient response, while maintaining a stable output voltage. By selecting the proper resistor-capacitor network from COMP to GND, the regulator response is optimized for a wide range of input voltages, output voltages, and load conditions.
SOFT START
To prevent input inrush current to the converter when the part is enabled, connect a capacitor from SS to GND to set the soft start period. Once the ADP1612/ADP1613 are turned on, SS sources 5 A, typical, to the soft start capacitor (CSS) until it reaches 1.2 V at startup. As the soft start capacitor charges, it limits the peak current allowed by the part. By slowly charging the soft start capacitor, the input current ramps slowly to prevent it from overshooting excessively at startup. When the ADP1612/ ADP1613 are in shutdown mode (EN 0.3 V), a thermal shutdown event occurs, or the input voltage is below the falling undervoltage lockout voltage, SS is internally shorted to GND to discharge the soft start capacitor.
Rev. A | Page 11 of 28
ADP1612/ADP1613
THERMAL SHUTDOWN (TSD)
The ADP1612/ADP1613 include TSD protection. If the die temperature exceeds 150C (typical), TSD turns off the NMOS power device, significantly reducing power dissipation in the device and preventing output voltage regulation. The NMOS power device remains off until the die temperature reduces to 130C (typical). The soft start capacitor is discharged during TSD to ensure low output voltage overshoot and inrush currents when regulation resumes.
ENABLE/SHUTDOWN CONTROL
The EN input turns the ADP1612/ADP1613 regulator on or off. Drive EN low to turn off the regulator and reduce the input current to 0.01 A, typical. Drive EN high to turn on the regulator. When the step-up dc-to-dc switching converter is in shutdown mode (EN 0.3 V), there is a dc path from the input to the output through the inductor and output rectifier. This causes the output voltage to remain slightly below the input voltage by the forward voltage of the rectifier, preventing the output voltage from dropping to ground when the regulator is shutdown. Figure 37 provides a circuit modification to disconnect the output voltage from the input voltage at shutdown. Regardless of the state of the EN pin, when a voltage is applied to VIN of the ADP1612/ADP1613, a large current spike occurs due to the nonisolated path through the inductor and diode between VIN and VOUT. The high current is a result of the output capacitor charging. The peak value is dependent on the inductor, output capacitor, and any load active on the output of the regulator.
UNDERVOLTAGE LOCKOUT (UVLO)
If the input voltage is below the UVLO threshold, the ADP1612/ ADP1613 automatically turn off the power switch and place the part into a low power consumption mode. This prevents potentially erratic operation at low input voltages and prevents the power device from turning on when the control circuitry cannot operate it. The UVLO levels have ~100 mV of hysteresis to ensure glitch free startup.
Rev. A | Page 12 of 28
ADP1612/ADP1613 APPLICATIONS INFORMATION
SETTING THE OUTPUT VOLTAGE
The ADP1612/ADP1613 feature an adjustable output voltage range of VIN to 20 V. The output voltage is set by the resistor voltage divider, R1 and R2, (see Figure 34) from the output voltage (VOUT) to the 1.235 V feedback input at FB. Use the following equation to determine the output voltage: VOUT = 1.235 x (1 + R1/R2) Choose R1 based on the following equation:
- 1.235 V R1 = R2 x OUT 1.235
(1)
For CCM duty cycles greater than 50% that occur with input voltages less than one-half the output voltage, slope compensation is required to maintain stability of the current-mode regulator. For stable current-mode operation, ensure that the selected inductance is equal to or greater than the minimum calculated inductance, LMIN, for the application parameters in the following equation:
L > L MIN =
(2)
(VOUT - 2 x VIN ) 2.7 x f SW
(7)
INDUCTOR SELECTION
The inductor is an essential part of the step-up switching converter. It stores energy during the on time of the power switch, and transfers that energy to the output through the output rectifier during the off time. To balance the tradeoffs between small inductor current ripple and efficiency, inductance values in the range of 4.7 H to 22 H are recommended. In general, lower inductance values have higher saturation current and lower series resistance for a given physical size. However, lower inductance results in a higher peak current that can lead to reduced efficiency and greater input and/or output ripple and noise. A peak-to-peak inductor ripple current close to 30% of the maximum dc input current typically yields an optimal compromise. For determining the inductor ripple current in continuous operation, the input (VIN) and output (VOUT) voltages determine the switch duty cycle (D) by the following equation:
D= VOUT - VIN VOUT
Inductors smaller than the 4.7 H to 22 H recommended range can be used as long as Equation 7 is satisfied for the given application. For input/output combinations that approach the 90% maximum duty cycle, doubling the inductor is recommended to ensure stable operation. Table 5 suggests a series of inductors for use with the ADP1612/ADP1613.
Table 5. Suggested Inductors
Manufacturer Sumida Part Series CMD4D11 CDRH4D28CNP CDRH5D18NP CDRH6D26HPNP DO3308P DO3316P D52LC D62LCB D63LCB WE-TPC WE-PD, PD2, PD3, PD4 Dimensions L x W x H (mm) 5.8 x 4.4 x 1.2 5.1 x 5.1 x 3.0 6.0 x 6.0 x 2.0 7.0 x 7.0 x 2.8 12.95 x 9.4 x 3.0 12.95 x 9.4 x 5.21 5.2 x 5.2 x 2.0 6.2 x 6.3 x 2.0 6.2 x 6.3 x 3.5 Assorted Assorted
Coilcraft Toko
(3)
Wurth Elektronik
Using the duty cycle and switching frequency, fSW, determine the on time by the following equation:
CHOOSING THE INPUT AND OUTPUT CAPACITORS
The ADP1612/ADP1613 require input and output bypass capacitors to supply transient currents while maintaining constant input and output voltages. Use a low equivalent series resistance (ESR), 10 F or greater input capacitor to prevent noise at the ADP1612/ADP1613 input. Place the capacitor between VIN and GND as close to the ADP1612/ADP1613 as possible. Ceramic capacitors are preferred because of their low ESR characteristics. Alternatively, use a high value, medium ESR capacitor in parallel with a 0.1 F low ESR capacitor as close to the ADP1612/ADP1613 as possible.
t ON =
D f SW
VIN x t ON L
(4)
The inductor ripple current (IL) in steady state is calculated by
I L =
(5)
Solve for the inductance value (L) by the following equation:
L=
VIN x t ON I L
(6)
Ensure that the peak inductor current (the maximum input current plus half the inductor ripple current) is below the rated saturation current of the inductor. Likewise, make sure that the maximum rated rms current of the inductor is greater than the maximum dc input current to the regulator.
Rev. A | Page 13 of 28
ADP1612/ADP1613
The output capacitor maintains the output voltage and supplies current to the load while the ADP1612/ADP1613 switch is on. The value and characteristics of the output capacitor greatly affect the output voltage ripple and stability of the regulator. A low ESR ceramic dielectric capacitor is preferred. The output voltage ripple (VOUT) is calculated as follows:
LOOP COMPENSATION
The ADP1612/ADP1613 use external components to compensate the regulator loop, allowing optimization of the loop dynamics for a given application. The step-up converter produces an undesirable right-half plane zero in the regulation feedback loop. This requires compensating the regulator such that the crossover frequency occurs well below the frequency of the right-half plane zero. The righthalf plane zero is determined by the following equation:
VOUT =
I xt QC = L ON COUT COUT
(8)
where: QC is the charge removed from the capacitor. tON is the on time of the switch. COUT is the output capacitance. IL is the average inductor current. t ON = and D f SW (9)
V FZ (RHP ) = IN V OUT
R LOAD x 2 x L
2
(13)
where: FZ(RHP) is the right-half plane zero. RLOAD is the equivalent load resistance or the output voltage divided by the load current. To stabilize the regulator, ensure that the regulator crossover frequency is less than or equal to one-fifth of the right-half plane zero. The regulator loop gain is AVL = V VFB x IN x G MEA x Z COMP x GCS x Z OUT VOUT VOUT (14)
- VIN V D = OUT VOUT
I L x (VOUT - VIN ) f SW x VOUT x VOUT
(10)
Choose the output capacitor based on the following equation:
C OUT (11)
Multilayer ceramic capacitors are recommended for this application.
DIODE SELECTION
The output rectifier conducts the inductor current to the output capacitor and load while the switch is off. For high efficiency, minimize the forward voltage drop of the diode. For this reason, Schottky rectifiers are recommended. However, for high voltage, high temperature applications, where the Schottky rectifier reverse leakage current becomes significant and can degrade efficiency, use an ultrafast junction diode. Ensure that the diode is rated to handle the average output load current. Many diode manufacturers derate the current capability of the diode as a function of the duty cycle. Verify that the output diode is rated to handle the average output load current with the minimum duty cycle. The minimum duty cycle of the ADP1612/ADP1613 is D MIN = VOUT - VIN ( MAX ) VOUT (12)
where: AVL is the loop gain. VFB is the feedback regulation voltage, 1.235 V. VOUT is the regulated output voltage. VIN is the input voltage. GMEA is the error amplifier transconductance gain. ZCOMP is the impedance of the series RC network from COMP to GND. GCS is the current sense transconductance gain (the inductor current divided by the voltage at COMP), which is internally set by the ADP1612/ADP1613. ZOUT is the impedance of the load and output capacitor.
where VIN(MAX) is the maximum input voltage. The following are suggested Schottky diode manufacturers: * * ON Semiconductor Diodes, Inc.
Rev. A | Page 14 of 28
ADP1612/ADP1613
To determine the crossover frequency, it is important to note that, at that frequency, the compensation impedance (ZCOMP) is dominated by a resistor, and the output impedance (ZOUT) is dominated by the impedance of an output capacitor. Therefore, when solving for the crossover frequency, the equation (by definition of the crossover frequency) is simplified to
V VFB x IN x G MEA x RCOMP x GCS x VOUT VOUT 1 =1 2 x f C x C OUT AVL = where: fC is the crossover frequency. RCOMP is the compensation resistor. Solve for RCOMP, RCOMP = 2 x f C x C OUT x (VOUT )2 VFB x VIN x G MEA x GCS (16)
The capacitor, C2, is chosen to cancel the zero introduced by output capacitance, ESR. Solve for C2 as follows:
C2 = ESR x C OUT RCOMP
(19)
(15)
For low ESR output capacitance such as with a ceramic capacitor, C2 is optional. For optimal transient performance, RCOMP and CCOMP might need to be adjusted by observing the load transient response of the ADP1612/ADP1613. For most applications, the compensation resistor should be within the range of 4.7 k to 100 k and the compensation capacitor should be within the range of 100 pF to 3.3 nF.
SOFT START CAPACITOR
Upon startup (EN 1.6 V), the voltage at SS ramps up slowly by charging the soft start capacitor (CSS) with an internal 5 A current source (ISS). As the soft start capacitor charges, it limits the peak current allowed by the part to prevent excessive overshoot at startup. The necessary soft start capacitor, CSS, for a specific overshoot and start-up time can be calculated for the maximum load condition when the part is at current limit by:
C SS = I SS (17) t VSS
where: VFB = 1.235 V. GMEA = 80 A/V. GCS = 13.4 A/V.
RCOMP 4746 x f C x C OUT x (VOUT ) 2 = VIN
(20)
Once the compensation resistor is known, set the zero formed by the compensation capacitor and resistor to one-fourth of the crossover frequency, or C COMP =
where: ISS = 5 A (typical). VSS = 1.2 V. t = startup time, at current limit. If the applied load does not place the part at current limit, the necessary CSS will be smaller. A 33 nF soft start capacitor results in negligible input current overshoot at start up, and therefore is suitable for most applications. However, if an unusually large output capacitor is used, a longer soft start period is required to prevent input inrush current. Conversely, if fast startup is a requirement, the soft start capacitor can be reduced or removed, allowing the ADP1612/ADP1613 to start quickly, but allowing greater peak switch current.
2 x f C x RCOMP
(18)
where CCOMP is the compensation capacitor.
ERROR AMPLIFIER FB 2 gm VBG COMP
1
RCOMP C2
06772-004
CCOMP
Figure 35. Compensation Components
Rev. A | Page 15 of 28
ADP1612/ADP1613 TYPICAL APPLICATION CIRCUITS
Both the ADP1612 and ADP1613 can be used in the application circuits in this section. The ADP1612 is geared toward applications requiring input voltages as low as 1.8 V, where the ADP1613 is more suited for applications needing the output power capabilities of a 2.0 A switch. The primary differences are shown in Table 6.
Table 6. ADP1612/ADP1613 Differences
Parameter Current Limit Input Voltage Range ADP1612 1.4 A 1.8 V to 5.5 V ADP1613 2.0 A 2.5 V to 5.5 V
STEP-UP REGULATOR CIRCUIT EXAMPLES
ADP1612 Step-Up Regulator
L1 4.7H VIN = 1.8V TO 4.2V
6
D1 3A, 40V VOUT = 5V VIN EN FB 2
7
SW 5 R1 30k COUT 10F
ON CIN 10F OFF
3
ADP1612
FREQ COMP 1 SS GND
4
R2 10k RCOMP 6.8k CCOMP 3300pF
8
CSS 33nF
The Step-Up Regulator Circuit Examples section recommends component values for several common input, output, and load conditions. The equations in the Applications Information section can be used to select components for alternate configurations.
L1: DO3316P-472ML D1: MBRA340T3G R1: RC0805FR-0730KL R2: CRCW080510K0FKEA RCOMP: RC0805JR-076K8L
CCOMP: ECJ-2VB1H332K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
STEP-UP REGULATOR
The circuit in Figure 36 shows the ADP1612/ADP1613 in a basic step-up configuration.
L1
Figure 38. ADP1612 Step-Up Regulator Configuration VOUT = 5 V, fSW = 650 kHz
100 90 80 VOUT = 5V fSW = 650kHz TA = 25C ADP1612
6
VIN EN
SW 5 R1 FB 2
EFFICIENCY (%)
VIN ON OFF CIN 650kHz (DEFAULT) 1.3MHz
7 3
ADP1612/ ADP1613
D1
VOUT
70
60 50
FREQ SS GND
4
R2 COMP 1 RCOMP CCOMP COUT
06772-005
8
CSS
40
VIN = 1.8V VIN = 2.7V VIN = 3.3V VIN = 4.2V 1 10 100 LOAD CURRENT (mA) 1k 10k
06772-041
30
Figure 36. Step-Up Regulator
The modified step-up circuit in Figure 37 incorporates true shutdown capability advantageous for battery-powered applications requiring low standby current. Driving the EN pin below 0.3 V shuts down the ADP1612/ADP1613 and completely disconnects the input from the output.
L1 NTGD1100L VIN R3 10k CIN Q1 A
Figure 39. ADP1612 Efficiency vs. Load Current VOUT = 5 V, fSW = 650 kHz
T
VOUT = 5V fSW = 650kHz
OUTPUT VOLTAGE (50mV/DIV) AC-COUPLED
ADP1612/ ADP1613
6 VIN
D1
VOUT
LOAD CURRENT (50mA/DIV)
SW 5 R1 FB 2 R2 COUT
06772-006
3 EN
Q1 B
1.3MHz 7 FREQ 650kHz (DEFAULT)
8 SS
ON OFF
CSS
RCOMP CCOMP
4
TIME (100s/DIV)
Figure 37. Step-Up Regulator with True Shutdown
Figure 40. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT = 5 V, fSW = 650 kHz
Rev. A | Page 16 of 28
06772-042
COMP 1 GND
06772-040
ADP1612/ADP1613
L1 4.7H VIN = 1.8V TO 4.2V
6
L1 10H D1 3A, 40V V OUT = 5V VIN = 2.7V TO 5V
6
D1 2A, 20V VOUT = 12V VIN EN FB 2
7
VIN EN
SW 5 R1 30k COUT 10F ON CIN 10F OFF
SW 5 R1 86.6k COUT 10F
ON CIN 10F OFF
3
ADP1612
FB 2
7
ADP1612
3
FREQ COMP 1 SS GND
4
R2 10k RCOMP 12k CCOMP 1200pF
FREQ COMP 1 SS GND
4
R2 10k RCOMP 22k CCOMP 1800pF
8
8
CSS 33nF
CSS 33nF
L1: DO3316P-472ML D1: MBRA340T3G R1: RC0805FR-0730KL R2: CRCW080510K0FKEA RCOMP: RC0805JR-0712KL
CCOMP: ECJ-2VB1H122K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
L1: DO3316P-103ML D1: DFLS220L-7 R1: ERJ-6ENF8662V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0722KL
CCOMP: ECJ-2VB1H182K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
06772-043
Figure 41. ADP1612 Step-Up Regulator Configuration VOUT = 5 V, fSW = 1.3 MHz
100 90 80
EFFICIENCY (%) EFFICIENCY (%)
Figure 44. ADP1612 Step-Up Regulator Configuration VOUT = 12 V, fSW = 650 kHz
100
VOUT = 5V fSW = 1.3MHz TA = 25C
ADP1612 90
VOUT = 12V fSW = 650kHz TA = 25C
ADP1612
80
70
70
60 50 40 VIN = 1.8V VIN = 2.7V VIN = 3.3V VIN = 4.2V
06772-044
60 VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V 1 10 100 LOAD CURRENT (mA) 1k
06772-047
50
30 1 10 100 LOAD CURRENT (mA) 1k 10k
40
Figure 42. ADP1612 Efficiency vs. Load Current VOUT = 5 V, fSW = 1.3 MHz
Figure 45. ADP1612 Efficiency vs. Load Current VOUT = 12 V, fSW = 650 kHz
T OUTPUT VOLTAGE (50mV/DIV) AC-COUPLED
VOUT = 5V fSW = 1.3MHz
T
VOUT = 12V fSW = 650kHz
OUTPUT VOLTAGE (100mV/DIV) AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
06772-045
TIME (100s/DIV)
TIME (100s/DIV)
Figure 43. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT = 5 V, fSW = 1.3 MHz
Figure 46. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT = 12 V, fSW = 650 kHz
Rev. A | Page 17 of 28
06772-048
06772-046
ADP1612/ADP1613
L1 6.8H VIN = 2.7V TO 5V
6
L1 15H D1 2A, 20V VOUT = 12V VIN = 2.7V TO 5V
6
D1 2A, 20V VOUT = 15V VIN EN FB 2
7
VIN EN
SW 5 R1 86.6k COUT 10F ON CIN 10F OFF
SW 5 R1 110k COUT 10F
ON CIN 10F OFF
3
ADP1612
FB 2
7
ADP1612
3
FREQ COMP 1 SS GND
4
R2 10k RCOMP 18k CCOMP 680pF
FREQ COMP 1 SS GND
4
R2 10k RCOMP 22k CCOMP 1800pF
8
8
CSS 33nF
CSS 33nF
L1: DO3316P-682ML D1: DFLS220L-7 R1: ERJ-6ENF8662V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0718KL
CCOMP: CC0805KRX7R9BB681 CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
L1: DO3316P-153ML D1: DFLS220L-7 R1: ERJ-6ENF1103V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0722KL
CCOMP: ECJ-2VB1H182K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
06772-049
Figure 47. ADP1612 Step-Up Regulator Configuration VOUT = 12 V, fSW = 1.3 MHz
100 90 80
EFFICIENCY (%) EFFICIENCY (%)
Figure 50. ADP1612 Step-Up Regulator Configuration VOUT = 15 V, fSW = 650 kHz
100
VOUT = 12V fSW = 1.3MHz TA = 25C
ADP1612 90
VOUT = 15V fSW = 650kHz TA = 25C
ADP1612
80
70
70
60 50 40 VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V
06772-050
60 VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V 1 10 100 LOAD CURRENT (mA) 1k
06772-053
50
30 1 10 100 LOAD CURRENT (mA) 1k
40
Figure 48. ADP1612 Efficiency vs. Load Current VOUT = 12 V, fSW = 1.3 MHz
Figure 51. ADP1612 Efficiency vs. Load Current VOUT = 15 V, fSW = 650 kHz
T OUTPUT VOLTAGE (100mV/DIV) AC-COUPLED
VOUT = 12V fSW = 1.3MHz
T
VOUT = 15V fSW = 650kHz
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
06772-051
TIME (100s/DIV)
TIME (100s/DIV)
Figure 49. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT = 12 V, fSW = 1.3 MHz
Figure 52. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT = 15 V, fSW = 650 kHz
Rev. A | Page 18 of 28
06772-054
06772-052
ADP1612/ADP1613
ADP1613 Step-Up Regulator
L1 10H VIN = 2.7V TO 5V
6
L1 10H D1 2A, 20V VOUT = 15V VIN = 2.7V TO 5V
6
D1 3A, 40V VOUT = 12V VIN EN FB 2
7
VIN EN
SW 5 R1 110k COUT 10F ON CIN 10F OFF
SW 5 R1 86.6k COUT 10F
ON CIN 10F OFF
3
ADP1612
FB 2
7
ADP1613
3
FREQ COMP 1 SS GND
4
R2 10k RCOMP 10k CCOMP 1800pF
FREQ COMP 1 SS GND
4
R2 10k RCOMP 12k CCOMP 2200pF
8
8
CSS 33nF
CSS 33nF
L1: DO3316P-103ML D1: DFLS220L-7 R1: ERJ-6ENF1103V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0710KL
CCOMP: ECJ-2VB1H182K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
L1: DO3316P-103ML D1: MBRA340T3G R1: ERJ-6ENF8662V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0712KL
CCOMP: ECJ-2VB1H222K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
06772-055
Figure 53. ADP1612 Step-Up Regulator Configuration VOUT =15 V, fSW = 1.3 MHz
100 90 VOUT = 15V fSW = 1.3MHz TA = 25C ADP1612 90 100
Figure 56. ADP1613 Step-Up Regulator Configuration VOUT = 12 V, fSW = 650 kHz
ADP1613
VOUT = 12V fSW = 650kHz TA = 25C
80
EFFICIENCY (%) EFFICIENCY (%)
80 70
70
60
60
50 VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V
06772-056
50 40 30 1 10 100 LOAD CURRENT (mA) 1k VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V
06772-059
40 30 1 10 100 LOAD CURRENT (mA)
1k
Figure 54. ADP1612 Efficiency vs. Load Current VOUT =15 V, fSW = 1.3 MHz
Figure 57. ADP1613 Efficiency vs. Load Current VOUT = 12 V, fSW = 650 kHz
T
VOUT = 15V fSW = 1.3MHz
T
VOUT = 12V fSW = 650kHz
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
TIME (100s/DIV)
TIME (100s/DIV)
Figure 55. ADP1612 50 mA to 150 mA Load Transient (VIN = 3.3 V) VOUT =15 V, fSW = 1.3 MHz
Figure 58. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 12 V, fSW = 650 kHz
Rev. A | Page 19 of 28
06772-060
06772-057
06772-058
ADP1612/ADP1613
L1 6.8H VIN = 2.7V TO 5V
6
L1 15H D1 3A, 40V VOUT = 12V VIN = 3.3V TO 5.5V
6
D1 3A, 40V VOUT = 15V VIN EN FB 2
7
VIN EN
SW 5 R1 86.6k COUT 10F ON CIN 10F OFF
SW 5 R1 110k COUT 10F
ON CIN 10F OFF
3
ADP1613
FB 2
7
ADP1613
3
FREQ COMP 1 SS GND
4
R2 10k RCOMP 10k CCOMP 1000pF
FREQ COMP 1 SS GND
4
R2 10k RCOMP 10k CCOMP 1800pF
8
8
CSS 33nF
CSS 33nF
L1: DO3316P-682ML D1: MBRA340T3G R1: ERJ-6ENF8662V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0710KL
CCOMP: ECJ-2VB1H102K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
L1: DO3316P-153ML D1: MBRA340T3G R1: ERJ-6ENF1103V R2: CRCW080510K0FKEA RCOMP: RC0805JR-0710KL
CCOMP: ECJ-2VB1H182K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
06772-061
Figure 59. ADP1613 Step-Up Regulator Configuration VOUT = 12 V, fSW = 1.3 MHz
100 90 VOUT = 12V fSW = 1.3MHz TA = 25C ADP1613 90 100
Figure 62. ADP1613 Step-Up Regulator Configuration VOUT = 15 V, fSW = 650 kHz
VOUT = 15V fSW = 650kHz TA = 25C
ADP1613
80
EFFICIENCY (%)
80
EFFICIENCY (%)
70
70
60
60
50 40 30 1 10 100 LOAD CURRENT (mA) 1k VIN = 2.7V VIN = 3.3V VIN = 4.2V VIN = 5.0V
06772-062
50 40 30 1 10 100 LOAD CURRENT (mA) 1k VIN = 3.3V VIN = 4.2V VIN = 5.0V VIN = 5.5V
06772-065
Figure 60. ADP1613 Efficiency vs. Load Current VOUT = 12 V, fSW = 1.3 MHz
Figure 63. ADP1613 Efficiency vs. Load Current VOUT = 15 V, fSW = 650 kHz
T OUTPUT VOLTAGE (100mV/DIV) AC-COUPLED
VOUT = 12V fSW = 1.3MHz
T
VOUT = 15V fSW = 650kHz
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
06772-063
TIME (100s/DIV)
TIME (100s/DIV)
Figure 61. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 12 V, fSW = 1.3 MHz
Figure 64. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 15 V, fSW = 650 kHz
Rev. A | Page 20 of 28
06772-066
06772-064
ADP1612/ADP1613
L1 10H VIN = 3.3V TO 5.5V
6
L1 15H D1 3A, 40V VOUT = 15V VIN = 3.3V TO 5.5V
6
D1 3A, 40V VOUT = 20V VIN EN FB 2
7
VIN EN
SW 5 R1 110k COUT 10F ON CIN 10F OFF
SW 5 R1 150k COUT 10F
ON CIN 10F OFF
3
ADP1613
FB 2
7
ADP1613
3
FREQ COMP 1 SS GND
4
R2 10k RCOMP 8.2k CCOMP 1200pF
FREQ COMP 1 SS GND
4
R2 10k RCOMP 18k CCOMP 820pF
8
8
CSS 33nF
CSS 33nF
L1: DO3316P-103ML D1: MBRA340T3G R1: ERJ-6ENF1103V R2: CRCW080510K0FKEA RCOMP: RC0805JR-078K2L
CCOMP: ECJ-2VB1H122K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
L1: DO3316P-153ML D1: MBRA340T3G R1: RC0805JR-07150KL R2: CRCW080510K0FKEA RCOMP: RC0805JR-0718KL
CCOMP: CC0805KRX7R9BB821 CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
06772-067
Figure 65. ADP1613 Step-Up Regulator Configuration VOUT = 15 V, fSW = 1.3 MHz
100 90 80
EFFICIENCY (%)
Figure 68. ADP1613 Step-Up Regulator Configuration VOUT = 20 V, fSW = 650 kHz
100
VOUT = 15V fSW = 1.3MHz TA = 25C
ADP1613 90
VOUT = 20V fSW = 650kHz TA = 25C
ADP1613
80
EFFICIENCY (%)
70 60 50 40 30 20 1 10 100 LOAD CURRENT (mA) 1k
70
60
50 VIN = 3.3V VIN = 4.2V VIN = 5.0V VIN = 5.5V
06772-068
40 30 1 10 100 LOAD CURRENT (mA)
VIN = 3.3V VIN = 4.2V VIN = 5.0V VIN = 5.5V 1k
06772-071
Figure 66. ADP1613 Efficiency vs. Load Current VOUT = 15 V, fSW = 1.3 MHz
Figure 69. ADP1613 Efficiency vs. Load Current VOUT = 20 V, fSW = 650 kHz
T
VOUT = 15V fSW = 1.3MHz
T
VOUT = 20V fSW = 650kHz
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
LOAD CURRENT (50mA/DIV)
LOAD CURRENT (50mA/DIV)
06772-069
TIME (100s/DIV)
TIME (100s/DIV)
Figure 67. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 15 V, fSW = 1.3 MHz
Figure 70. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 20 V, fSW = 650 kHz
Rev. A | Page 21 of 28
06772-072
06772-070
ADP1612/ADP1613
L1 10H VIN = 3.3V TO 5.5V
6
SEPIC CONVERTER
D1 3A, 40V VOUT = 20V
VIN EN
SW 5 R1 150k COUT 10F
ON CIN 10F OFF
3
ADP1613
FB 2
7
FREQ COMP 1 SS GND
4
R2 10k RCOMP 8.2k CCOMP 1200pF
The circuit in Figure 74 shows the ADP1612/ADP1613 in a single-ended primary inductance converter (SEPIC) topology. This topology is useful for an unregulated input voltage, such as a battery-powered application in which the input voltage can vary between 2.7 V to 5 V and the regulated output voltage falls within the input voltage range. The input and the output are dc isolated by a coupling capacitor (C1). In steady state, the average voltage of C1 is the input voltage. When the ADP1612/ADP1613 switch turns on and the diode turns off, the input voltage provides energy to L1 and C1 provides energy to L2. When the ADP1612/ADP1613 switch turns off and the diode turns on, the energy in L1 and L2 is released to charge the output capacitor (COUT) and the coupling capacitor (C1) and to supply current to the load.
L1 DO3316P 4.7H
8
CSS 33nF
L1: DO3316P-103ML D1: MBRA340T3G R1: RC0805JR-07150KL R2: CRCW080510K0FKEA RCOMP: RC0805JR-078K2L
CCOMP: ECL-2VB1H122K CIN: GRM21BR61C106KE15L COUT: GRM32DR71E106KA12L CSS: ECJ-2VB1H333K
Figure 71. ADP1613 Step-Up Regulator Configuration VOUT = 20 V, fSW = 1.3 MHz
100 90 80
EFFICIENCY (%)
VOUT = 20V fSW = 1.3MHz TA = 25C
ADP1613
06772-073
VIN = 2.0V TO 5.5V
6
ADP1612/ ADP1613
VIN EN FREQ SS GND
4
C1 10F SW 5
MBRA210LT 2A, 10V
VOUT = 3.3V
70
CIN 10F
ON OFF
3
L2 DO3316P 4.7H FB 2 COMP 1 RCOMP 82k CCOMP 220pF
60 50
CSS
7
R1 16.9k
8
R2 10k
COUT 10F
06772-008
40 30 20 1 10 100 LOAD CURRENT (mA)
VIN = 3.3V VIN = 4.2V VIN = 5.0V VIN = 5.5V 1k
06772-074
Figure 74. SEPIC Converter
TFT LCD BIAS SUPPLY
Figure 75 shows a power supply circuit for TFT LCD module applications. This circuit has +10 V, -5 V, and +22 V outputs. The +10 V is generated in the step-up configuration. The -5 V and +22 V are generated by the charge-pump circuit. During the step-up operation, the SW node switches between +10 V and ground (neglecting the forward drop of the diode and on resistance of the switch). When the SW node is high, C5 charges up to +10 V. When the SW node is low, C5 holds its charge and forward-biases D8 to charge C6 to -10 V. The Zener diode (D9) clamps and regulates the output to -5 V. The VGH output is generated in a similar manner by the chargepump capacitors, C1, C2, and C4. The output voltage is tripled and regulated down to 22 V by the Zener diode, D5.
Figure 72. ADP1613 Efficiency vs. Load Current VOUT = 20 V, fSW = 1.3 MHz
T OUTPUT VOLTAGE (200mV/DIV) AC-COUPLED
VOUT = 20V fSW = 1.3MHz
LOAD CURRENT (50mA/DIV)
TIME (100s/DIV)
Figure 73. ADP1613 50 mA to 150 mA Load Transient (VIN = 5 V) VOUT = 20 V, fSW = 1.3 MHz
06772-075
Rev. A | Page 22 of 28
ADP1612/ADP1613
BAV99 R4 200 C6 10F D7 DO3316P 4.7H D2 BAV99 D8 C5 10nF D4 C1 10nF BAV99 D3 C2 1F C4 10nF D5 C3 10F R3 200 D5 BZT52C22 VGH +22V
D9 BZT52C5VIS
VGL -5V
VIN = 3.3V
6
ADP1612/ ADP1613
VIN EN FB 2
7
D1 SW 5 R1 71.5k
VOUT = 10V
ON CIN 10F OFF 1.3MHz 650kHz (DEFAULT) FREQ SS GND
4 3
R2 10k COMP 1 RCOMP 27k CCOMP 1200pF COUT 10F
06772-007
8
CSS
Figure 75. TFT LCD Bias Supply
Rev. A | Page 23 of 28
ADP1612/ADP1613 PCB LAYOUT GUIDELINES
For high efficiency, good regulation, and stability, a welldesigned printed circuit board layout is required. Use the following guidelines when designing printed circuit boards (also see Figure 34 for a block diagram and Figure 3 for a pin configuration).
*
*
*
* *
06772-076
Figure 76. Example Layout for ADP1612/ADP1613 Boost Application (Top Layer)
*
*
*
Keep the low ESR input capacitor, CIN (labeled as C7 in Figure 76), close to VIN and GND. This minimizes noise injected into the part from board parasitic inductance. Keep the high current path from CIN (labeled as C7 in Figure 76) through the L1 inductor to SW and GND as short as possible. Keep the high current path from VIN through L1, the rectifier (D1) and the output capacitor, COUT (labeled as C4 in Figure 76) as short as possible. Keep high current traces as short and as wide as possible. Place the feedback resistors as close to FB as possible to prevent noise pickup. Connect the ground of the feedback network directly to an AGND plane that makes a Kelvin connection to the GND pin. Place the compensation components as close as possible to COMP. Connect the ground of the compensation network directly to an AGND plane that makes a Kelvin connection to the GND pin. Connect the softstart capacitor, CSS (labeled as C1 in Figure 76) as close to the device as possible. Connect the ground of the softstart capacitor to an AGND plane that makes a Kelvin connection to the GND pin. Avoid routing high impedance traces from the compensation and feedback resistors near any node connected to SW or near the inductor to prevent radiated noise injection.
Figure 77. Example Layout for ADP1612/ADP1613 Boost Application (Bottom Layer)
Rev. A | Page 24 of 28
06772-077
ADP1612/ADP1613 OUTLINE DIMENSIONS
3.20 3.00 2.80
8
5
3.20 3.00 2.80 PIN 1 IDENTIFIER
1
5.15 4.90 4.65
4
0.65 BSC 0.95 0.85 0.75 0.15 0.05 COPLANARITY 0.10 0.40 0.25 15 MAX 1.10 MAX 0.70 0.55 0.40
091709-A
6 0
0.23 0.13
COMPLIANT TO JEDEC STANDARDS MO-187-AA
Figure 78. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters
ORDERING GUIDE
Model ADP1612ARMZ-R7 1 ADP1613ARMZ-R71 ADP1612-5-EVALZ1 ADP1612-BL1-EVZ1 ADP1613-12-EVALZ1 ADP1613-BL1-EVZ1
1
Temperature Range -40C to +125C -40C to +125C
Package Description 8-Lead Mini Small Outline Package [MSOP] 8-Lead Mini Small Outline Package [MSOP] Evaluation Board, 5 V Output Voltage Configuration Blank Evaluation Board Evaluation Board, 12 V Output Voltage Configuration Blank Evaluation Board
Package Option RM-8 RM-8
Branding L7Z L96
Z = RoHS Compliant Part.
Rev. A | Page 25 of 28
ADP1612/ADP1613 NOTES
Rev. A | Page 26 of 28
ADP1612/ADP1613 NOTES
Rev. A | Page 27 of 28
ADP1612/ADP1613 NOTES
(c)2009 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D06772-0-9/09(A)
Rev. A | Page 28 of 28

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